Radio control apparatus



Feb. 23, 1960 R. GOLLUB 2,926,240

RADIO CONTROL APPARATUS Original Filed Sept. 7, 1954 3 Sheets-Sheet 1 Fig.1. '2

DISCRIMINATOR AND I RECTIFIER OSCILLATOR I TANK CIRCUIT i CONTROLLABLE CURRENT SOURCE I '2 R.F.AMPLIFIER INPUT CIRCUIT I 52 R.F. AMPLIFIER OUTPUT CIRCUIT 3 48 B 4% INVENTOR II--.I,.-.

RAPHAEL GOLLUB v v v- T 59 ATTORNEYS admit/1 Feb. 23, 1960 R. GOLLUB RADIO CONTROL APPARATUS Original Filed Sept. 7, 1954 3 Sheets-Sheet 2 RAPHAEL GOLLUB r Emnm mwBom I l l I J 0 odd I w;

t. n u 38.50 m :MMEWEME w 1 m mwEw zoc m 5565 E 053 m l i l: -11 1: mm mm L m on QM Feb. 23, 1960 R. GOLLUB RADIO CONTROL APPARATUS Original Filed Sept. 7, 1954 3 Sheets-Sheet 3 J B m w L n w m M m m A m H PM 3 In E A m R F m 0 I m o 9 m C v N U la m G 6 MN m RM EE 5% m ww w 3 HAND SWITCH A l JTTJMATIC STATION SELECTOR SWITCHES MANUAL STATION SELECTOR FooT swrrcu United States Patent RADIO CONTRUL APPARATUS Raphael Gollub, Stamford, Conn, assignor to C.G.S. I

Laboratories, Inc, Stamford, Conn.

Original application September 7, 1954, Serial No. 454,256. Divided and this application October 14, 1955, Serial No. 544,155 I 6 Claims. (Cl. 2502il) This application is a division of my earlier application, Serial Number 454,256, for Electrical Control Apparatus, filed September 7, 1954.

The present invention relates to electrical control apparatus and more particularly to such apparatus adapted for use with or including controllable inductors.

The present invention is described as embodied in a remotely controllable radio receiver system of a type utilizing a controllable inductor to regulate the frequency to which the radio is tuned. The system described is enabled to be quickly and easily installed in an automobile and the component 1 parts easily changed, the receiver chassis being removed simply by unplugging three plugs.

Among the many advantages of the control apparatus described are those resulting from the fact that it provides easy remote control from either the front or rear seat of the automobile.

Another advantage ofthe radio control system described is that it is well adapted for use with superheterodyne receivers and enables remote control of the tuning of the radio frequency and oscillator circuits in such a receiver while providing automatic tracking of the tuning frequencies of these circuits.

Among the advantages of the apparatus described are those resulting from the fact that the controllable inductor used provides improved control characteristics and enables tuning over a wide frequency range. Controllable inductors customarily include a control winding wound on a magnetically saturable core with a signal winding wound on a portion of the core-so that changes in the degree of magnetic saturation of the core regulate the inductance of the signal winding which is connected into a circuit to be controlled. A control current is passed through the control winding in order to control the magnetic saturation of the core. As the control current is increased the magnetic saturation of the core increases, reducing the permeability of the material associated with the signal winding and hence reducing its inductance. When the control current is reduced, the inductance of the signal winding increases.

in present day controllable inductors one of the problems encountered is that the core material retains a substantial degree of residual magnetism in the absence of any control current, thus preventing the inductance of the signal winding from rising to as high a value as could be obtained if the core material became fully unsaturated. Considerable efforts have been made in the past in order to neutralize this residual magnetism and thus obtain wider ranges of inductance change, for example, William D. Gabor in copending application Serial No. 279,825, now abandoned, assigned to a common assignee with the present application, discloses a system using control current to neutralize the residual flux. I have found that a substantial reduction in the residual flux and an improvement in the control characteristics of controllable inductors is obtained by the use of nonmagnetic shims located in the path of the control flux.

2,92%,2ib Patented Feb. 23, 3.930

In the controllable inductor described, a plurality of separate signal windings each with its own individual signal core portion are all controlled by the same control winding on a common control yoke. In this inductor non-magnetic electrically conductive shims are sandwiched between each side of all the signal core portions and the control yoke.

Other aspects and advantages of the present invention will be understood from the following description of a remote control receiver incorporating the invention and adapted for installation in an automobile, when considered in conjunction with the accompanying drawing in-which: r

Figure l is a diagrammatic view of an automobile showing the arrangement of a radio receiver embodying the present invention;

Figure 2 is an enlarged front view of the steering wheel showing the controls for the radio mounted in the center of the steering wheel;

Figure 3 is a schematic circuit diagram of the radio receiver and control circuits of an automobile radio incorporating the invention;

Figure 4 is a schematic circuit diagram of the wiring and connections for the remote control of the receiver of Figure 3;

Figure 5 shows, partly diagrammatically and partly in perspective, an electrically-controllable inductor which forms part of the auto radio receiver shown in Figure 3, the shielding structure being omitted to show the construction;

Figure 6 is an elevational view of the inductor of Figure 5, the control winding being shown diagrammatically and in section;

Figure 7 is an enlarged view of one of the three variable-inductance signal circuits of the inductor of Figure 5;

Figure 8 is a perspective view of another embodiment of the inductor of Figure 5, the control winding being indicated diagrammatically; and

Figure 9 is an elevational view of the inductor of Figure 8.

The automobile radio receiver shown in the drawings is divided into a number of separate components with plugs and sockets at convenient points in the system. The receiver chassis 10, which is located in a convenient place in the automobile, for example in the rear trunk as shown in Figure 1, includes all of the circuit elements shown in Figure 3 except the antenna 12 and the loudspeaker 14.

As shown in Figure 2, controls for the radio are positioned on the hub of the steering wheel. These include a manual station selector 16, which may be adjusted by the driver to tune the receiver to various stations, a combined on-oif switch and volume control 18, a tone control 20, and an automatic station selector push-button switch 22. Momentary closure of switch 22 causes the receiver to tune itself to a radio station on an adjacent frequency. A foot switch 23 near the drivers position controlsthe receiver in the same manner as the switch 22. The connections from the controls on the steering Wheel extend down inside of the steering column 24.

In the receiver chassis it) is a radio frequency amplifier stage 26 (Figure 3), an oscillator and frequency converter stage 28, a tuned intermediate frequency amplifier 30, an audio frequency detector stage 32, a first audio amplifier stage 33 and an audio power amplifier stage 34. A frequency control network 35 is provided to stabilize the oscillator and is connected to a control amplifier 36 to tune automatically the radio-frequency circuits by regulating the control current through a winding 37, as explained in detail hereindter. An automatic carrierseeking control 38 is provided so that whenever the control button 22 or 23 is depressed the receiver will automatically tune to another station.

In order remotely to control receiver 10, an electricallycontrollable inductor is provided having three radio-frequency control circuits A, B, and C, with the control winding 37 associated therewith for regulating their in ductances in accordance with the position of the station selector 16.

In one embodiment of the present invention, the controllable inductor circuits A, B, and C (see also Figures 5, 6, and 7) include ferrite core portions 40, 42, and 44 respectively, with signal windings 46, 48 and 50 wound thereon. The core portions 40, 42, and 44 are bridged across between the legs of a U-shaped magnetic control core portion 52 having the control winding 37 in two series connected portions and one portion being around each of the two legs 54-1 and 54-2 of the control yoke.

The control winding portions are connected in flux aiding relationship on the control yoke 52 so that any control current flowing through winding 37 regulates the degree of magnetic saturation of signal core portions 40, 42, and 44.

As shown in detm'l in Figure 7, each of the signal core portions, for example the core portion 42, comprises two elongated bars of ferrite or ferro-magnetic ceramic placed longitudinally adjacent one another. This ferrite material may be similar to that disclosed by Snoek in US. Patents Nos. 2,452,529; 2,452,530; and 2,452,531. A generally elongated hexagonal signal winding opening 56 is formed by trapezoidal recesses in the adjoining sides of the two bars. The signal winding 48 associated with core 42 is in two halves extending through the opening 56 and connected in series, so that their magnetic fields are in aiding relationship around the opening 56 to induce flux flowing around opening 56, as indicated by arrows 58. Whereas, the control flux, in flowing between the legs 54-1 and 54-2, follows paths extending substantially the full length of the core 42 as indicated by the arrows 59 so that the control and signal flux fields are not mutually coupled. The signal flux 58 is alternating in direction, while the control flux 59 may be a generally unidirectional flux whose value is varied only as necessary to regulate the degree of magnetic saturation of the core 42 and particularly the saturation of the edges of core 42 adjacent the hole 56 on which the two halves of winding 48 are wound. The permeability of the ferrite material in the core 42 decreases rather strikingly with an increase in the degree of its magnetic saturation produced by the control flux 59, and thus the inductance in the control circuit B is changed in accordance with the control current in winding 37. Similarly, the inductance in control circuits A and C is controlled by the control current in winding 37, because their cores 40 and 44 are bridged across between the yoke legs 54-1 and 54-2 and are subjected to the substantially same degree of saturation as core 42. Thus, the inductance values of windings 46, 48, and 50 track each other.

In order to reduce substantially any residual magnetism in control core 52 or in signal cores 40, 42, and 44 when the control current in winding 37 is decreased, it is advantageous to use non-magnetic shims 60 to space the ends of the signal cores slightly from the legs 54-1 and 54-2. These shims also provide further magnetic isolation between cores 40, 42, and 44, and legs 54-1 and 54-2 and act to confine the signal flux 58 to the signal cores. To be most effective in reducing residual magnetism the shims 60 should be at least 10 mils thick. The shims adjacent the sides of the legs 54-1 and 54-2 are preferably considerably thicker than the shims between the ends of these legs and the core 40. In the receiver shown the two shims at the ends of the legs 54-1 and 54-2 are 10 mils thick and those adjacent the sides of the legs are 30 mils thick. The reason for the thinner shims at the ends of the legs 54-1 and 54-2 is that the end core 40 receives less of the control flux than the cores 42 and 44 because it is further from the control winding 37. Also, the core 40 is adjacent the ends of the laminations and so does not have as good magnetic coupling because of any slight irregularities in the ends of the laminations. This ratio in the thickness of the res :ective shims 60 may be varied where the dimensions of the control and signal cores are changed or a different lamination arrangement is used. If added shielding effeet is desired, the shims 60 may be electrically conductive, further preventing any signal flux from entering the control core 52. I find that shims 60 which are of brass 30 and 10 mils thick are well suited for a radio receiver as shown, providing reduction in residual magnetism and giving suitable isolation of the signal and control cores, as well as providing optimum control of the inductance in circuits A, B. and C by the control current.

In the receiver shown the control core 52 comprised a stack of 13 laminations of cold rolled carbon steel, for example such as SAE 1010 with a No. 4 temper and maximum Rockwell hardness B65. The laminations are .030 thick making a total stack of .390 inch. The laminations are 1 /8 inches wide and 2 7 inches long. The legs 54-1 and 54-2 are .312 inch wide, with a 1 inch spacing between them, and the back of the core 52 is inch wide. The control winding 37 comprises two bobbins of 20,000 turns each of No. 40 enameled wire connected in series, making a total of 40,000 turns. Each of the signal cores 40, 42, and 44 comprise two rods of ferrite, each A; inch square in cross-section and about 1 inches long, so as to overlap the core legs by slightly more than l inch at each side. The shims 60 are slightly larger than the area of the signal cores in contact with the control core. The signal cores may more fully overlap the legs of the control core, as shown in the drawings, when longer rods of ferrite are used, but I find the particular dimensions described quite satisfactory.

The hexagonal opening 56 in the signal cores 40, 42, and 44 is about inch long, the thin portions of the signal cores are about inch long, and the cross-sections of these thin portions are $1 by A; inch. The signal windings 46, 48, and 50 each have a total of turns of Litz wire, 60 turns being wound around each side of the openings 56. The antenna may be coupled to the core 40 by a winding 73 having about 3 turns through the opening 56 in the core 40.

For best operation the core portion 40 for the input to the R1 stage 26 is usually placed across the ends of legs 54-1 and 54-2 as isolating it more completely from the oscillator circuit, with the cores 42 and 44 being bridged across the sides of these legs. A shield of electrically-conductive material 61 is fitted between the core 40 and the cores 42 and 44, and an outer parabolic shield 62 is spaced from and curved around the outside of cores 40, 42, and 44. It is soldered to the edges of shield 61 as shown in Figure 6.

The radio-frequency control circuit A is included in the tuned circuitin the input of the radio frequency ampliiier stage 26, and control circuit C is included in the tuned circuit in the output of this stage. Control circuit B is in the oscillator tank circuit. The control current in winding 37 regulates the inductance of the circuits A, and C and hence controls the frequency to which the receiver 16 is tuned, as explained in detail hereinafter.

The incoming radio signals picked up on the antenna 12 are coupled from a primary winding 73 (see also Figure 5) on the core 40 to the winding 46 forming a secondary winding and into the tuned input circuit connected between the common return (ground) circuit of the receiver 10 and the grid 74 of a pentode 75. The primary and secondary windings 73 and 46, respectively, on the core 40 form an antenna coupling transformer having certain advantages discussed hereafter. The tuned inputcircuit is. formed by the winding 46 having one end coupled to ground through a condenser 76 and its other end connected to the grid 74, with a fixed condenser 77 in parallel with a padding condenser 78 connected across the winding 46 and the condenser 76. a

The pentode 75 has a cathode 79 connected to ground, a screen grid 80 connected through a condenser -81 to ground, a suppressor grid 82 connected to the cathode, with its plate 83 connected to a tuned plate load circuit including a condenser 84 connected to ground and shunted by an adjustable condenser 85. The other end of the inductance winding 50 is coupled to ground through the condenser 81 and is connected through a filter resistor 86 and a lead 87 to a power supply 62 indicated diagrammatically in block form. The power supply 62 is conventional and has a vibrator connected to the automobile battery 65 (Figure 1) and avoltage step-up circuit to supply a suitably filtered direct high voltage between its output terminals 63 and 64.

The amplified RF. signal is coupled from the plate 83 through a coupling condenser 88 and across a grid resistor 89 to a grid of an oscillator convertor tube .90 whose cathode 91 is coupled to ground through a radio frequency choke 92 and is also connected by a lead 93 to the oscillator tank circuit, generally indicated at ment 96 is connected to the common ground circuit of the receiver chassis and across both the windings 48 and 95, with the junction of the windings 95 and 96 being coupled through a lead 98, a:coupling condenser 99 and across a grid resistor 101 to a grid of the tube 90. The other side of the parallel resonant tank circuit includes a condenser 104 connected between the common ground and the lead 93 with a condenser 106 in parallel with an adjustable condenser 108 being connected between leads 93 and 98.

The screen grids of the tube 90 are coupled to ground through a condenser 112 and are connected to the power supply 62 through a filter resistor 114.

OPERATION OF THE REMOTE CONTROL CIRCUITS For purposes of explanation, it isassumed that the re- .ceiver 10 is a broadcast receiver tunable through arange from 530 to 1650 kilocycles, or in other words, a frequency range of somewhat more than 3 to 1. To tune through this range the inductance values in circuits A and B must change by a ratio of approximately 10m 1. This is well within the available range of inductance varations obtainable by using apparatus as shown in Figures 5, 6, and 7; this apparatus can readily produce inductance changes of 100 to l and often produces inother words, a range of something more than 2 to 1, re-

quiring an inductance change of about to 1. As mentioned above, both circuits A and B must be varied over an inductance range of approximately to l. The inductance in circuit B also varies over a range of 10 to l, but by using the pair of padding inductance windings 95 and 96 in series and parallel therewith, respectively, the total effective change'in the inductance of the resonant tank circuit 94 is adjusted to the required range of about 5 to 1. By using the proper values for inductances 95 and 96 the frequency of the oscillator 28 is caused to track 455 kc. above the frequency to which the tuned input and output circuits of the RF. stage 26 are adjusted,

ciated with the control amplifier 36. The inductance of circuits A and .C are forced to follow or track with the value of circuit B, which is sensed and controlled as desired, and thus circuit B acts as the bellwether" for the station selecting circuits as a whole.

The oscillator signal appearing across the oscillator tank circuit 94 is fed through a lead to the top of a series discriminator circuit formed by a resistor 122 in series with an inductor 124, and a grounded condenser 126. The inductor 124 and the condenser 126 are tuned to have a series resonant frequency somewhat above the maximum oscillator frequency. In the particular circuit shown, with a maximum oscillator frequency of about 2105 kc. this discriminator circuit may be tuned about 50 or 100 kc. higher, for example, may be tuned to 2150 kc. Thus, the discriminator including elements 122 124, 126 has a negative output slope, for as the oscillator frequency increases, the impedance of the discriminator decreases. Consequently, the magnitude of the rectified signal, which is fed from the junction of the resistor .122 and the inductor '124is decreased,- This output is fed'through a rectifier -128 -and appears acrossa resistor 1-30 in parallel with a condenser 132, connected between ground and output terminal 133 of network 38. Since the rectifier 128 is arranged to pass only the negative half 'cycles of the output from the discriminator, the potential of the terminal 133 is always negative with respect to the .common ground circuit. The terminal 133 has its greatbelow the minimum oscillator frequency. Thus, regardless of the oscillator frequency, the full amplitude A of the oscillations in the tank circuit 94 is fed to the rectifier 134, which is arranged to pass only positive half cycles. Thus, a positive voltage is fed to an output terminal 135 of the circuit 38. This positive voltage appears across a condenser 139 and is always equal in magnitude to A /2, so that the terminal 135 is always A 2 volts above the terminal 133.

in summary of the operation of the discriminator and rectifier circuit 38, the terminal 133 is at a large negative voltage when'the oscillator is at minimum frequency, and this terminal 133 gradually movesnp and. almost reaches zero voltage when the oscillator is at maximum frequency. The terminal 135 is always A 2 volts above terminal 133. Thus, terminal 135 is at a small positive voltage when the oscillator is at minimum frequency and gradually moves up to a large positive voltage when the oscillator is at maximum frequency.

As will be explained in connection with the description of the remote control circuits, depending upon the positions of a switch 140 (Figure 3) and a switch 141 between the terminals 133 and 135. -'Assuming that the potentiometer 144 controlled by the manual stationselector 16 on the steering-wheel is connected across terminals 133- and 13S,--then some point along potentiometer 144 is at-zero orground potential because terminail-1'33 is always'below and terminal 135 is always above zero. The position of this zero point depends upon the oscillator frequency at-that time. -When the oscillator is at minimum'frequency, the zero voltage point on potentiometer 14-4'is near its left terminal 153. As the oscillator frequency increases, this zero voltage point shifts along potentiometer 144 toward its right terminal 152.

The potentiometer 144 is inseries between resistors 151 and 157 so that every point-along-the potentiometer 144 -will adjust to zero voltage, thus providing a range of adjustment corresponding withfull scale width of the knob 16.

An important advantage :of the present invention is that the position of this zero voltage-point depends upon therelative voltages between terminals 136. and 135 and ground, both of which voltages are proportionately affected by any changes in oscillator amplitude A. Thus, the position of the zero voltage point on potentiometer 144 is independent of the oscillator amplitude and depends only upon the oscillator frequency. A given point .on potentiometer 144 always corresponds with the same oscillator frequency and similarly withpotentiometers 144a and 144i; when they are being used to control the receiver.

"The manual-control 16 is used to, move an adjustable contact 153 along the potentiometer 144. If the adjustable contact 153 is at a position along potentiometcr144 which differs from the zero voltage point, this dilference or error voltage is fed to the grid 154 (Figure v3 of .a pentode 155 in the DC. control amplifier circuit 36. The output from the plate 156 of the pentode 55 is direct coupled to the grid 1580f atriode to control the current fiow through thecontro'l winding 37, which is connected by a lead 162 between the plate 16-4, of the triode 160 and the power supply 62.

To compensate for fluctuations in the voltage from the power supply 62 .or from the automobile battery 65 due to changes in load which might affect the temperature of the cathode 166 of pentode 155, a voltagedropping network is provided, including two fixed resistors 168 and 170, and a potentiometer 172. The potentiometer 17?. is used to ndiustthe midpoint ofzthe operating range o the controllable inductor. The adjustable contact 174 of potentiometer-1.72, is connected to the cathode 17,6 and is moved to a position along the potentiometer 172 giving the best compensation and the best operating range. With the tube used in the embodiment described, the contact 174 should be adjusted to bias the cathode about 1.0 volt positive with respect to the common ground when the battery 64 is supplying normal voltage. This 1.0 volt adjustment-is such that with zero voltage applied to the grid 154, the current through the con- .trol winding37 tunes the receiver to the middle of the broadcast frequency band. Moreover, the 1.0 volt bias adjustment gives excellent compensation over a full 10% iiuctuation in battery voltage, for as the battery voltage drops, lowering the temperature and hence the work function .of the cathode 176, the voltage from the power .supplygfierminal-pdfialsogdrops so that the cathode bias is correspondingly reduced to compensate for the work function reduction.

Moreover, due to its own heat storage capacity, the temperature of the cathode ,176 tends to lag behind rapid changes in the batter-y voltage. In order to delay the changes in the'bias ofthe cathode 176 so that any fluctuations in bias will occur at the same rateas any changes in cathode temperature, a large electrolytic condenser 177 is connected to ground from the junction of the resistors 16.8 an .11 s mat the im cqnstant fo m y t resistor 168 and the condenser 177 is elfectively equal to the thermal time :lag of the cathode 176.

In case the particular .pentode being used is sensitive to voltage fluctuations of its screen 178, this screen is connected .to another voltage-dropping network including three resistors 180, 182, and 184 in series between the power supply terminal 63 and the common ground circuit. To isolate the screen from any voltage fluctuations in the power lead 87, the junction of resistors 180 and132 isconnected to a-neon voltage regulating tube 135 having its-other terminal grounded. The plate of the lpeutode 1'55 :is'connected through its plate load resistor 186 to .the power supply terminal 63 and advantage- .ously is coupled to ground through a fairly large condenser 190, which reduces the frequency response and stabilizes the control amplifier 36 so that it is essentially a direct current .amplifier.

The cathode 192 of :the triode is biased to the proper operating range by a third voltage-dropping networkincluding resistors 194 and 196 connected between the power. supply terminal .63 and ground, with the cathode 192 being connected to their junction. Preferably, the

resistors 19.4 and 196 are made as small as operation will at a position along-the potentiometer 144 corresponding to a radio station to which .the automobile driver has been listening. The driver, wishing to listen to another station on axhigher frequency moves the contact 153 counterclockwise along the potentiometer 144. This feeds a negativevoltage to the grid 154 of the pentode 155.

The voltage of its plate 154 increasesand biases the grid 158 more positive so that an increased current flows through the triode and through the control winding .37. Thisincrease in control current increases the saturation of the three cores .40, 42 and 44 and reduces the inductance in circuits A, B, and C, and hence raises the frequency to which the receiver 10 is tuned.

This increase in frequency immediately causes the discriminating and rectifying circuit.35 to shift the voltage of both of the terminals 133 and 135 in the positive direction causing the new point on potentiometer 144 to which the contact 153 has been moved to shift up toward zero voltage with respect to the common ground circuit. The voltage fed'to the grid 154 moves back toward zero, preventingany'further current change through the control winding 37 andthus holding the receiver 10 tuned to the newfrequency corresponding to the new position of the contact 153.

When the contact 153 is moved clockwise along the potentiometer 144,-the operation of the control circuit is the opposite of that described above, and the receiver 10 is tunedto a lower frequency.

Among the important advantages of the remote station selecting control circuits described, is that the frequency of the oscillator stage 28 is continually sensed or meas- .ured by the discriminator and rectifier circuit 35. Any changes in the oscillatorfrequency for any reason, cause a different signal to be fed to the grid 154 of the DC. amplifier stage 36, thus changing the current through the control winding means 37 to bring the oscillator frequency back to the desired frequency. In effect, the operation of the remote tuning circuits is dependent only upon the values of the three elements in the discriminator circuit, that is, upon the resistor 122, inductor 124 and condenser 126. These three elements are arranged to be Substantially insensitive to changes in temperature, and hence the operation of the remote tuning circuits as a whole is made independent of temperature changes.

.Moreover, the station selecting circuits are made substantially independent of any tendency toward hysteresis ,etfectinthe controlled inductance values in circuits A, ,B,

and C, .for as mentioned above'a given position on any to the frequency corresponding with that position on the dial 16. The magnitude of the controlcurrent auto matically adjusts itself to overcome any tendency toward magnetic hysteresis in the control flux.

The operation of the automatic station selecting circuit 38 is similar to that of the manual circuit just described, the position of the movable contact 153b along the potentiometer 144b being controlled by a unidirectional motor200 connected between the power supply terminal a3 and the plate 202 of a pentode 2%. When the listener wishes to cause the automatic selector to tune the receiver to the next station, he depresses one of the switches 22 or 23, discharging a condenser 204 connected to the grid 205 of the pentode 203 to drop this grid to ground potential. A large current then flows from the power supply through the motor 200 and the tube 203to ground. This causes the motor 200 to turn and move the contact 15312 counterclockwise along the potentiometer 144b. As soon as the receiver is tuned to the next stat-ion having a carrier of sufficient strength at antenna 12 for proper reception, an automatic control voltage is fed through a resistor 206 to bias the grid 205 to a cut-off voltage, stopping the current through the motor 200. The potentiometer 14% is arranged in 'a substantially complete circle so that as the listener tunes from station to station the contact 153b moves counterclockwise toward the terminal 15%. As soon as the contact 153b has passed the position on the potentiometer corresponding to the last station near the top of the broadcast band having a sufficiently strong carrier signal for proper reception, the contact 153b jumps from terminal 15% over to terminal 152k and begins around potentiometer 144b again. Thus, in operation, the automatic station selector starts at the bottom of the broadcast band and moves up to the top then jumps to the bottom and progresses toward the top again. The screen 207 of the tube 203 is connected to a grounded condenser 210 and to the junction of a pair of resistors 208 and 209 in a voltage dropping network connected between the power supply terminal 63 and a cathode resistor 212, which also provides fixed bias for the cathode 214.

To provide the maximum sensitivity of control in order to hold the receiver 10 closely tuned to any desired station, the oscillator 68 is preferably operated at substantially the full amplitude permitted by the rating of the tube 90 used.

Among the advantages of the circuit described are that they provided remote control of the receiver; that they eliminate all moving parts; and that they provide a receiver of longer life and one which is more rugged in operation because of the elimination of the moving parts. Moreover, for reasons which are not fully understood the receiver circuit described actually operates in a manner considerably superior to that of the ordinary heterodyne receiver having the same number of tubes in the radio portion of the receiver. This receiver as disclosed has better than a microvolt of sensitivity, that is,

a microvolt impressed on the antenna 12 produces a signal in the loud speaker 14 which is at least twice as loud as the background noise. One of the possible explanations for the superiority of the receiver disclosed is that the inductance to capacitance ratio of the tuned plate circuit in the RF. amplifier is considerably lower than is customary in standard superheterodyne sets. This advantageously enables the use of a pentode 90 which 10 has a much larger transconductance than is usually'pos sible in an ordinary superheterodyne receiver.

Moreover, there are certain important fundamental differences in the operation of a receiver wherein the condenser values are fixed and the inductance values are changed from the operation of an ordinary receiver in which the inductance values are fixed and the condensers are changed in value. Some of these differences are not at all apparent and are rather surprising in their results, as will be pointed out in the following description. In the ordinary superheterodyne receiver in order to increase the frequency, the capacitance is decreased while the inductance remains constant. Thus, as the frequency is increased, the impedance of the resonant circuits involved is increased due to the fixed inductances involved.- The increase in impedance tends to cause regeneration problems. Moreover, it decreases the effective gain at the higher frequencies because of. the presence of shunt or stray capacities to ground which are present in any circuit. Also, the losses in the fixed inductances increase,so that the Q" drops and, thus, the band-widths drops.

'In contrast to this, in the present circuit with increasing frequency the effective impedance of the tuned circuits preferably remains constant. In addition, due to the de crease in inductance (which also means a decrease in various losses in the inductance) there is a corresponding increase in the Q of the circuits being used. The result is that the effective band-width of the receiver is constant over the full range'of reception, and moreover the effective gain of the receiver is constant because the impedance remains constant with increasing frequency. 1

The reason that the band-width is constant is that it is proportional to the ratio.of the frequency and Q. That is: BWocF/Q. As the frequency rises the Q is correspondingly increased so that the ratio remains approximately constant, and hence the band-width is approximately constant throughout the full range of operation of the receiver.

Another advantage of the present invention is that it is not the absolute values of the inductances which are important in the operation, but rather their normalized values, that is, the ratio of the incremental inductance at any point to the incremental inductance when the control current is zero. This is particularly helpful in the antenna circuit because it enables the use of a wide variety of antennas, the only requirement being that the total 'volume and shape of the antenna loop winding 73 be maintained the same. Thus, any configuration of antenna may be used and will produce results superior to those in the ordinary receiversused today.

Although the present receiver is described as tunable over a range from 530 to 1650 kc., the inductance values of the control circuits A, B, and C are capable of variations over ranges of to 1 or even 200 to 1. Thus, it

is apparent that the method of the present invention is capable of use for tuning a receiver over a far wider range than is done today with mechanically variable condensers.

be used with two other similar controllable inductors (not shown) to provide the control circuits A, B, and C in receiver 10. The controllable inductor 240 has a control winding 37a which in operation is connected between the leads 162 and 87 in series with the corresponding control windings (not shown) of the other two similar controllable inductors, mentioned above, as will be understood. This inductor 240 includes a signal core portion 42a carrying a winding 48a similar to the core 42 and winding 48 in the control circuit B. Core 42a is bridged across between a pair of copper shims 60a resting against the side legs 242-1 and 242-2 of a control core portion 52a. The control winding 37a is wound on the back part of the core 52a. The core 52a is made of a flexible ,11 magnetizable material, for example a strap of soft iron bent into a U shape to form the two side legs 242 and 243, with the ends of the side legs being bent over again toward one another in a spaced overlapping relationship .to-form a magnetic path for the control flux between legs 242 and 243 in shunt with the path through the core 42a. An adjustment of the effective reluctance of this shunt path is provided by a large-headed machine screw 244 of non-magnetic material threaded through a hole in the outer end of the leg 242 and resting against .the inner end of the leg 243. By tightening it, this shunt reluctance is increased, so that for any given value of the current in the control winding 37a the degree of magnetic saturation of the signal core portion 42a is increased lowering the effective inductance of the :winding 43a thereon. In

:overall effect tightening the screw 24-4 is equivalent to adding some turns in the winding 37a.

When the three inductors similar to inductor 2% have their control windings connected in series there may be deviations of the controlled inductance values in circuits A, B, and C from one another, so that due to individual differences they do not track properly. The shunt control flux path adjustment by the screw 244 enables compensations to be made for the individual deviations so thatthe inductance values are caused to track one another.

Another adjustment for tracking characteristics is provided by changing the reluctance in series with the control flux path through the core 42a with a nonmagnetic machine screw 248 which serves to skew the right shim .60a to change the effective length of the reluctance region between the right end of the core 42a and the leg 243. To facilitate the tilting of this shim, the end of the screw may be rounded to fit in a socket in the-shim. By adjusting the screws 244 and 248 all of the controllable inductors 240 used can be adjusted to track one another as desired.

Among the. advantages of using separate controllable inductors instead of having them ganged upon a single control yoke 42 is that each of them may then be located closely adjacent the portion of the receiver circuit desired, thus advantageously enabling the use of shorter interconnecting wires within the receiver.

REMOTE CONTROL CIRCUITS AND INTERCON- NECTIONS All, of the connections to the receiver chassis ,10 are made through three sockets: an antenna lead-in socket .250 (Figure 1), a loudspeaker outlet252, and a control and power socket 254. The antenna is mounted on the automobile near the receiver chassis for example, it may be fastened on the rearburnper or on the rearof the car nearthe top of the trunk, as shown in Figure .1, with .its lead-in wire adapted to be plugged into the'socket 250.

The loudspeaker 14 is located remotely from the chassis 10; for example, under a grill in the rear Window ledge with-its leads 256 plugged into the socket 252..

A seven-wire control and power cable 260 extends between a plug 261 in the receiver socket 254 and a socket 262 adjacent the steering post 24 and the floorbo ds- To permit control of the radio from the rear seat, a

branch cable 264 extends from the cable 260. to atsocket .mobile battery 65 through a lead .272 and theig tion switch 274 to the socket 262. The leads;frorn the con- -trols on the steering wheel pass down inside ofthe steeringcolumn 24 some going directly to a plug 280 adapted to. connect with the, socket 262; others are connected through the. switch 141 to the plug 280. The switch 141 is located adjacent the plug 280 wherethe driver can operate it with his foot. It switches the connections to permit the radio to be operated by the controls on the steering column or by the extension control unit 268.

When the switch 141 is in its left-hand position, as viewed in Figure. 4, it connects the steering wheel controls to the receiver, and when it is in its other position, ,it connects the receiver to the extension control unit 268 through an instrument panel socket 282. With the switch 14 in one position, all of the steering-wheel controls except the on-ofi switch are disconnected from .the system, and the extension unit 263 base plug 269 which can be plugged into either socket 282 or 266 to enable either the person next tothe driver or one in the rear seat to operate the receiver when it is turned on.

Assuming that the ignition switch is on and that the switch 141 is in the left position so that the steering wheel controls are operative, the driver turns the receiver on by closing an on-off switch 283 ganged to a volume control potentiometer contact 284. From the socket 262, the current for the receiver is supplied through the plug 280, a lead 285, the on-otf switch 283, a lead 286, the

control switch 141, a lead 288, the plug 280 and-the socket 262, and a lead 288 in the cable 260 to the plug 261. The socket 254 (Figure 3), which receives the plug 261, provides a continuation of the lead 288 through the solenoid of a stepping relay 290 to the power supply 62. The lead 288 is arranged by connection X also to supply the heater circuits of the vacuum tubes in the radio. These circuits are conventional and have been omitted from the drawings.

The volume control potentiometer has one end connccted to the common ground return circuit of the automobile. Its other end is connected through a lead 296 and the switch 141, a lead 298 in the cable 260, the plug 261, the socket 254 (Figure 3), and the continuation of the lead 2% in the radio chassis to a coupling condenser 300 at the output of the first audio amplifier stage 38. The slidable contact 284 of the potentiometer is connected through a tone-control potentiometer 304, the slidable contact of which is coupled through a capacitor 305 to ground, then through a lead 306, the

switch 141, and a lead 308, through the plug cable connections described above and through the lead 308 in the chassis 10 (Figure 3) to the control grid 309 of a pentode vacuum tube in the audio power amplifier stage 34.

In order to change the receiver from manual control to automatic control, the stepping relay 2% is actuated merely by turning the power off and on. The stepping relay 290 moves a double-pole double-throw switch between its upper or automatic carrier-seeking control position and its lower or manual control position. Turning the power off and on again returns the receiver to manual control.

Assuming that switch 140 is in its manual control position, then the manual station selector 16 and potentiometer 144 (Figure 4) controls the frequency to which the receiver is tuned, as explained above. The circuit from the output terminal 135 through the potentiometer 144 and back to the output terminal 133 can be followed through the switch 140, a lead 320, the cable and switch connections already described, and a lead 122 to the potentiometer terminal 152. The circuit from the other terminal of the potentiometer 144 is returned through a lead 324, which by-passes the switch 141 and a lead 326 through the cable connections to the output terminal 133 of the discriminating and detecting circuit 35. The movable contact 153 of the potentiometer 144 controls the voltage applied to the input grid 154 (Figure 3) of the direct current amplifier 36. This circuit can be traced from the potentiometer 13 contact 153 through a lead 332, the switch 141 and a lead 334 through the cable connections tothe switch 140 and from the switch 140 through a lead 336 to the control grid 154.

In addition to the foot button 23 (Figure 4) the driver is provided with the switch 22 on the steering wheel which may be used when the receiver is adjusted for automatic carrier-seeking operation. Switch 22 is connected to the same lead 337in the cable 260 as is the foot switch 23, the connection being made by means of a lead 340, and the switch 141.

When the switch 140 (Figure 3) is in its upper automatic carrier-seeking control position, the driver may depress either switch'22 on the steering wheel or the foot switch 23 to cause the receiver to jump from the station to which it is tuned'to the next station having a signal at antenna 12 of sufiicient intensity for proper reception, the selection of the stations being controlled by the circuit 38, as already explained.

Looking at the right side of Figure 4, it is seen that the extension control 268 includes duplicates of the controls that are provided for the driver, with the exception of a foot switch. The various components of extension unit 268 performing functions similar to the drivers controls have similar reference numerals followed by the suffix a. When the plug 269 is removed from the instrument panel socket 282 and plugged into the rear seat socket 266, as indicated in phantom lines, the passengers in the rear of the car have full remote control of the receiver, except that the on-ofl switch 282a has no control over the receiver because there is no socket lead for plug 266 corresponding to the, top prong of the plug 269, the driver thus being able to turn the receiver onor off by the switch 282.

CIRCUIT PARAMETERS, CIRCUIT DETAILS AND CALCULATIONS In a particular embodiment of the present invention the connections from the oscillator stage through the remainder of the radio circuit are as follows:

The output from the plate 342 of the oscillator convertor tube 90 is fed to the first IF transformer 346 having its primary and secondary windings 347 and 348, respectively, shunted by condensers 350 and 351 connected to ground through a condenser 352. The IF signal from the secondary 348 is fed to the grid 353 of a pentode 354 having a cathode 355 connected to ground through a resistor 356. The output from the plate 358 of the tube 354 is fed through a second IF transformer 346a, including components similar to those of the first IF transformer, to the cathode 360 of a detector tube 362. The rectified signal appearing at the plate 364 of the tube 362 is filtered by a pi-filter formed by a pair condensers 365 and 366 shunted to ground with a series filter resistor 368 connected therebetween. The audio signal appearing across a resistor 372 in parallel with the condenser 366, is coupledthrough condenser 374 across a grid return resistor 375 to the grid 376 of a triode 377 having its cathode 378 grounded and its plate 380 connected to the condenser 300 and also connected through a load resistor 382 to the power supply terminal 63. A small condenser 384 across the load 382 provides filtering and proper tone balance.

The voltage from the detector plate 364 is also used as an automatic volume control voltage and is fed from the resistor 206 through another filter resistor 365 and across a filter condenser 366 and through an isolating resistor 368 to the grid 353 of the first IF amplifier tube 354 to control its gain and through a resistor 400 to the grid of the RRF amplifier tube 75 to control its gain.

As described above, the audio signals from the audio stage 33 pass through the volume and tone control circuits and then back to the grid 309 of the pentode 310 Whose cathode 402 is connected to ground through a cathode bias resistor 404 shunted by a condenser 406 and with 14 its plate 408 connected through theprimary 410 of a loud speaker matching transformer 412, whose secondary 414 is connected through the plug 252 and the leads 256 to the loud speaker 14.

In this embodiment the following values were used for the components and circuit parameters as listed:

Tubes:

6U8 185 NE-Z 310 6N6 354 6BA6 362 377i Resistors: Ohms 86 1,000 89 120,000 101 22,000 114 1,000 122 10,000 130 300,000 144 100,000 151 6,200 157 68,000 168 100,000 170 47,000 172 1,000 47,000 182 75,000 184 36,000 186 1,000,000 194 10,000, 2 watt 196 18,000 356 100 368 470,000 400 470,000

Condensers: In micro farads 78 Variable 7 to 45x10 81 .01 85 Variable 7 to. 45X 10- 88 .01 99 "33x10" 112 .01 12s 1o 10 r132 .01 136 .01 139 .01 177 100x 10* 2 352 .01 369 .01

Receiver Frequency Oscillator Frequency Now evaluating three determinants:

1 12 1 2) 1 -919 -23l X .0 l

m- Ye From the foregoingoalculations it will be understood that the effective capacitance in the oscillator tank circuit is equal to the effective capacitance in a resonant circuit in the radio frequency tuning stage divided by about 1.6; In order to obtain proper tracking, the fixed inductor in series with the variable inductance tuning element 48 in the tank circuit has a value of about 54 micro henries while the inductor 96 in parallel with them has about 40 times this value, being about 2 millihenries.

Assuming that a different value of C was used, for example such as 320 micro microfarads, being 8 times the value used in the sample calculations above but that the same relative frequencies and same tracking coincidence points are used, then the value of C is also 8 times as large but L and L are about Ms as large.

From the foregoing description it will be understood that the present invention provides a remote control radio receiver system having many advantages as discussed above, and it is understood that the system described can be adapted to a wide variety of different applications and that various changes or modifications may be made therein, each as may be best suited to the particular application desired and that the scope of the present invention is intended to include such modifications or adaptations, as defined by the following claims limited only by the prior art.

What is claimed is:

1. An automobile radio receiver system including a radio receiver remote from the location of a seat in the automobile, station selection tuning means within the receiver including a radio frequency amplifier circuit and an oscillator circuit, variable inductance means including magnetically saturable core means and at least two signal windings wound on said core means, first circuit means conneotingone of said signal windings in said radio frequency amplifier circuit and second circuit means connecting the other of said signal windings in said oscillator circuit, control winding means for regulating the inductance of said signal windings, for tuning the receiver to different radio stations, a controllable source of current for said tuning element, said source of current having an output circuit, first circuit means between the output circuit of said source of current and said tuning element for supplying controlled amounts of current to said element, said controllable source of current having a control circuit for controlling the amounts of current supplied from the output circuit, second circuit means extending from the control circuit of said source of current to a point near said seat, first detachable electrical connection means in said second circuit means at said point, discriminator means in said receiver responsive to the tuning frequency, rectifier means connected to the output of said discriminator, third circuit means extending from said rectifier to said point, second detachable electrical connection means in said third circuit means at said point, and an extension control including third and fourth detachable elecrical connection means adapted to engage said first and second detachable electrical connection means, respectively, and a variable resistance station selecting control connected between said third and fourth detachable connection means.

2. An electrically tunable radio receiver system comprising a receiver including a radio frequency amplifier circuit and an oscillator circuit, variable inductance means including magnetically saturable core means and at least two signal windings wound on said core means, first circuit means connecting one of said signal windings in said radio frequency amplifier circuit and second circuit means connecting the other of said signal windings in said osciila-tor circuit, control winding means for regulating the inductance of said signal windings, a discriminator circuit having its input connected to said oscillator circuit, rectifier means connected to the output .of said discriminator circuit and arranged to produce a unidirectional output voltage, first detachable electrical connection means including first and second contacts, said first contact being connected to said rectifier means to receive said unidirectional voltage, current amplifier means connected to said control winding means for sending current through said control winding means, said second contact being connected to said current amplifier means, variable resistance means, and second detachable electrical connection means including third and fourth contacts connected to said variable resistance means and adapted to engage said first and second contacts when said first and second detachable electrical connection means are engaged.

3. An automobile radio receiver system comprising a radio receiver including a radio frequency amplifier circuit and an cscillator circuit, variable inductance means including magnetically saturable core means and at least two signal windings wound on said core means, first circuit means connecting one of said signal windings in said radio frequency amplifier circuit and second circuit means connecting the other of said signal windings in said oscillator circuit, control winding means for regulating the inductance of both of the signal windings, an amplifier connected to said control Winding means for supplying current to said control Winding means, said amplifier having an input circuit for controlling the amount of current sup plied to said control winding means, a seat in said automobile, detachable electrical connection means adjacent said seat, said connection means having at least a first and a second contact, first circuit means between said first contact of said detachable electrical connection means and said input circuit, a frequency discriminator connected to said oscillator circuit, rectifier means coupled to the output of said discriminator, second circuit means connected from said rectifier means to said second contact, and a station selection control having third and fourth contacts for engaging said first and second contacts, respectively, and a variable resistor in circuit between said third and fourth contacts.

4. An automobile radio receiver system as claimed in claim 3 and wherein said detachable electrical connection means are provided adjacent both the front and rear seats in the automobile.

5. An automobile radio receiver tuning system including a radio receiver chassis including a radio frequency amplifier circuit, an oscillator circuit, and variable inductance apparatus including magnetically saturable core elements, at least two signal windings wound on said core elements, first circuit means coupling one of said signal windings into said radio frequency amplifier circuit, second circuit means coupling another of said signal windings into said oscillator circuit, electromagnetic control means magnetically coupled to said core elements for regulating the degree of saturation thereof for controlling the effective inductance of said signal windings, thereby to control the tuning of said system, a discriminator circuit having its input connected to said oscillator circuit, rectifier means connected to the output of said discriminator circuit for producing a direct current output voltage as a function of the frequency to which said oscillator circuit is tuned, first detachable electrical connection means including first and second contacts, third circuit means connecting said first contact to the output of said rectifier means, fourth circuit means coupling said second contact to said electromagnetic control means, variable resistance means, second detachable electrical connection means including third and fourth contacts connected to said variable resistance means and adapted to engage said first and second contacts when said first and second detachable electrical connection means are engaged.

6. An automobile receiver tuning system as claimed in claim 5 and wherein said first detachable electrical connection means includes a fifth contact also connected to the output of said rectifier means, and said second detachable electrical connection means includes a sixth contact connected to the opposite 'side of said variable resistance, means from said third contact and adapted to engage said fifth contact, and a slider on said variable resistance means connected to said fourth contact.

References Cited in the file of this patent UNITED STATES PATENTS 2,034,773 Van Roberts Mar. 24, 1936 2,163,646 Ware June 27, 1939 2,255,915 De Kramolin Sept. 16, 1941 2,268,619 Reid Jan. 6, 1942 2,326,737 Andrews Aug. 17, 1943 2,445,031 McDonald July 13, 1948 2,580,254 Summerhayes Dec. 25, 1951 2,581,202 Post Jan. 1, 1952 2,622,146 Sontheimer Dec. 16, 1952 2,809,289 Harris Oct. 8, 1957 FOREIGN PATENTS 447,104 Great Britain May 12, 1936 

